Variable bandwidth filter for dimmer phase angle measurements

Description

RELATED APPLICATIONS

The present disclosure claims priority to U.S. Provisional Patent Application Ser. No. 61/756,732, filed Jan. 25, 2013, which is incorporated by reference herein in its entirety.

FIELD OF DISCLOSURE

The present disclosure relates in general to the field of electronics, and more specifically to systems and methods for ensuring compatibility between one or more low-power lamps and the power infrastructure to which they are coupled.

BACKGROUND

Many electronic systems include circuits, such as switching power converters or transformers that interface with a dimmer. The interfacing circuits deliver power to a load in accordance with the dimming level set by the dimmer. For example, in a lighting system, dimmers provide an input signal to a lighting system. The input signal represents a dimming level that causes the lighting system to adjust power delivered to a lamp, and, thus, depending on the dimming level, increase or decrease the brightness of the lamp. Many different types of dimmers exist. In general, dimmers generate an output signal in which a portion of an alternating current (“AC”) input signal is removed or zeroed out. For example, some analog-based dimmers utilize a triode for alternating current (“triac”) device to modulate a phase angle of each cycle of an alternating current supply voltage. This modulation of the phase angle of the supply voltage is also commonly referred to as “phase cutting” the supply voltage. Phase cutting the supply voltage reduces the average power supplied to a load, such as a lighting system, and thereby controls the energy provided to the load.

A particular type of a triac-based, phase-cutting dimmer is known as a leading-edge dimmer. A leading-edge dimmer phase cuts from the beginning of an AC cycle, such that during the phase-cut angle, the dimmer is “off” and supplies no output voltage to its load, and then turns “on” after the phase-cut angle and passes phase cut input signal to its load. To ensure proper operation, the load must provide to the leading-edge dimmer a load current sufficient to maintain an inrush current above a current necessary for opening the triac. Due to the sudden increase in voltage provided by the dimmer and the presence of capacitors in the dimmer, the current that must be provided is typically substantially higher than the steady state current necessary for triac conduction. Additionally, in steady state operation, the load must provide to the dimmer a load current to remain above another threshold known as a “hold current” needed to prevent premature disconnection of the triac.

FIG. 1 depicts a lighting system 100 that includes a triac-based leading-edge dimmer 102 and a lamp 142. FIG. 2 depicts example voltage and current graphs associated with lighting system 100. Referring to FIGS. 1 and 2, lighting system 100 receives an AC supply voltage V_SUPPLY from voltage supply 104. The supply voltage V_SUPPLY is, for example, a nominally 60 Hz/110 V line voltage in the United States of America or a nominally 50 Hz/220 V line voltage in Europe. Triac 106 acts as a voltage-driven switch, and a gate terminal 108 of triac 106 controls current flow between the first terminal 110 and the second terminal 112. A gate voltage V_G on the gate terminal 108 above a firing threshold voltage value V_F will cause triac 106 to turn ON, in turn causing a short of capacitor 121 and allowing current to flow through triac 106 and dimmer 102 to generate an output current i_DIM.

Assuming a resistive load for lamp 142, the dimmer output voltage V_{Φ_DIM} is zero volts from the beginning of each of half cycles 202 and 204 at respective times t₀ and t₂ until the gate voltage V_G reaches the firing threshold voltage value V_F. Dimmer output voltage V_{Φ_DIM} represents the output voltage of dimmer 102. During timer period t_OFF, the dimmer 102 chops or cuts the supply voltage V_SUPPLY so that the dimmer output voltage V_{Φ_DIM} remains at zero volts during time period t_OFF. At time t₁, the gate voltage V_G reaches the firing threshold value V_F, and triac 106 begins conducting. Once triac 106 turns ON, the dimmer voltage V_{Φ_DIM} tracks the supply voltage V_SUPPLY during time period t_ON.

Once triac 106 turns ON, the current i_DIM drawn from triac 106 must exceed an attach current i_ATT in order to sustain the inrush current through triac 106 above a threshold current necessary for opening triac 106. In addition, once triac 106 turns ON, triac 106 continues to conduct current i_DIM regardless of the value of the gate voltage V_G as long as the current i_DIM remains above a holding current value i_HC. The attach current value i_ATT and the holding current value i_HC is a function of the physical characteristics of the triac 106. Once the current i_DIM drops below the holding current value i_HC, i.e. i_DIM<i_HC, triac 106 turns OFF (i.e., stops conducting), until the gate voltage V_G again reaches the firing threshold value V_F. In many traditional applications, the holding current value i_HC is generally low enough so that, ideally, the current i_DIM drops below the holding current value i_HC when the supply voltage V_SUPPLY is approximately zero volts near the end of the half cycle 202 at time t₂.

The variable resistor 114 in series with the parallel connected resistor 116 and capacitor 118 form a timing circuit 115 to control the time t₁ at which the gate voltage V_G reaches the firing threshold value V_F. Increasing the resistance of variable resistor 114 increases the time t_OFF, and decreasing the resistance of variable resistor 114 decreases the time t_OFF. The resistance value of the variable resistor 114 effectively sets a dimming value for lamp 142. Diac 119 provides current flow into the gate terminal 108 of triac 106. The dimmer 102 also includes an inductor choke 120 to smooth the dimmer output voltage V_{Φ_DIM}. Triac-based dimmer 102 also includes a capacitor 121 connected across triac 106 and inductor choke 120 to reduce electro-magnetic interference.

Ideally, modulating the phase angle of the dimmer output voltage V_{Φ_DIM} effectively turns the lamp 142 OFF during time period t_OFF and ON during time period t_ON for each half cycle of the supply voltage V_SUPPLY. Thus, ideally, the dimmer 102 effectively controls the average energy supplied to lamp 142 in accordance with the dimmer output voltage V_{Φ_DIM}.

Another particular type of phase-cutting dimmer is known as a trailing-edge dimmer. A trailing-edge dimmer phase cuts from the end of an AC cycle, such that during the phase-cut angle, the dimmer is “off” and supplies no output voltage to its load, but is “on” before the phase-cut angle and in an ideal case passes a waveform proportional to its input voltage to its load.

FIG. 3 depicts a lighting system 300 that includes a trailing-edge, phase-cut dimmer 302 and a lamp 342. FIG. 4 depicts example voltage and current graphs associated with lighting system 300. Referring to FIGS. 3 and 4, lighting system 300 receives an AC supply voltage V_SUPPLY from voltage supply 304. The supply voltage V_SUPPLY, indicated by voltage waveform 400, is, for example, a nominally 60 Hz/110 V line voltage in the United States of America or a nominally 50 Hz/220 V line voltage in Europe. Trailing-edge dimmer 302 phase cuts trailing edges, such as trailing edges 402 and 404, of each half cycle of supply voltage V_SUPPLY. Since each half cycle of supply voltage V_SUPPLY is 180 degrees of the supply voltage V_SUPPLY, the trailing-edge dimmer 302 phase cuts the supply voltage V_SUPPLY at an angle greater than 0 degrees and less than 180 degrees. The phase cut, input voltage V_{Φ_DIM} to lamp 342 represents a dimming level that causes the lighting system 300 to adjust power delivered to lamp 342, and, thus, depending on the dimming level, increase or decrease the brightness of lamp 342.

Dimmer 302 includes a timer controller 310 that generates dimmer control signal DCS to control a duty cycle of switch 312. The duty cycle of switch 312 is a pulse width (e.g., times t₁-t₀) divided by a period of the dimmer control signal (e.g., times t₃-t₀) for each cycle of the dimmer control signal DCS. Timer controller 310 converts a desired dimming level into the duty cycle for switch 312. The duty cycle of the dimmer control signal DCS is decreased for lower dimming levels (i.e., higher brightness for lamp 342) and increased for higher dimming levels. During a pulse (e.g., pulse 406 and pulse 408) of the dimmer control signal DCS, switch 312 conducts (i.e., is “on”), and dimmer 302 enters a low resistance state. In the low resistance state of dimmer 302, the resistance of switch 312 is, for example, less than or equal to 10 ohms. During the low resistance state of switch 312, the phase cut, input voltage V_{Φ_DIM} tracks the input supply voltage V_SUPPLY and dimmer 302 transfers a dimmer current i_DIM to lamp 342.

When timer controller 310 causes the pulse 406 of dimmer control signal DCS to end, dimmer control signal DCS turns switch 312 off, which causes dimmer 302 to enter a high resistance state (i.e., turns off). In the high resistance state of dimmer 302, the resistance of switch 312 is, for example, greater than 1 kiloohm Dimmer 302 includes a capacitor 314, which charges to the supply voltage V_SUPPLY during each pulse of the dimmer control signal DCS. In both the high and low resistance states of dimmer 302, the capacitor 314 remains connected across switch 312. When switch 312 is off and dimmer 302 enters the high resistance state, the voltage V_C across capacitor 314 increases (e.g., between times t₁ and t₂ and between times t₄ and t₅). The rate of increase is a function of the amount of capacitance C of capacitor 314 and the input impedance of lamp 342. If effective input resistance of lamp 342 is low enough, it permits a high enough value of the dimmer current i_DIM to allow the phase cut, input voltage V_{Φ_DIM} to decay to a zero crossing (e.g., at times t₂ and t₅) before the next pulse of the dimmer control signal DCS.

Dimming a light source with dimmers saves energy when operating a light source and also allows a user to adjust the intensity of the light source to a desired level. In an LED lighting system, there may exist a desire to maintain very narrow bandwidths in filtering control signals used to set the amount of light to be output by the LEDs (e.g., to reject noise, dimmer phase variation, other alternating current phenomena). However, there may also exist an opposing desire to maintain higher bandwidths to quickly respond to changes in a control setting of a dimmer. Such contrary requirements are not easily solved using traditional approaches, such as use of classic-low-pass filters or leaky integrators.

SUMMARY

In accordance with the teachings of the present disclosure, certain disadvantages and problems associated with ensuring compatibility of a low-power lamp with a dimmer and a transformer may be reduced or eliminated.

In accordance with embodiments of the present disclosure, an apparatus may include a variable bandwidth filter having an input for receiving an input signal and an output for generating an output signal. The output signal may be generated by filtering the input signal in conformity with a variable bandwidth of the variable bandwidth filter. The variable bandwidth may be set based on an integrated error between the input signal and the output signal.

In accordance with these and other embodiments, a method may include generating an output signal from an input signal by filtering the input signal in conformity with a variable bandwidth of a variable bandwidth filter. The method may also include setting the variable bandwidth based on an integrated error between the input signal and the output signal.

Technical advantages of the present disclosure may be readily apparent to one of ordinary skill in the art from the figures, description and claims included herein. The objects and advantages of the embodiments will be realized and achieved at least by the elements, features, and combinations particularly pointed out in the claims.

It is to be understood that both the foregoing general description and the following detailed description are examples and explanatory and are not restrictive of the claims set forth in this disclosure.

BRIEF DESCRIPTION OF THE DRAWINGS

A more complete understanding of the present embodiments and advantages thereof may be acquired by referring to the following description taken in conjunction with the accompanying drawings, in which like reference numbers indicate like features, and wherein:

FIG. 1 illustrates a lighting system that includes a triac-based leading-edge dimmer, as is known in the art;

FIG. 2 illustrates example voltage and current graphs associated with the lighting system depicted in FIG. 1, as is known in the art;

FIG. 3 illustrates a lighting system that includes a phase-cut trailing-edge dimmer, as is known in the art;

FIG. 4 illustrates example voltage and current graphs associated with the lighting system depicted in FIG. 3, as is known in the art;

FIG. 5 illustrates an example lighting system including a controller for implementing a variable bandwidth filter for dimmer phase angle measurements, in accordance with embodiments of the present disclosure;

FIG. 6 illustrates an example phase filtering combination for use in the lighting system depicted in FIG. 5, in accordance with embodiments of the present disclosure; and

FIGS. 7A and 7B depict example integrator filters for use in the variable bandwidth filter depicted in FIG. 6, in accordance with embodiments of the present disclosure.

DETAILED DESCRIPTION

FIG. 5 illustrates an example lighting system 500 including a controller 512 for implementing a variable bandwidth filter for dimmer phase angle measurements in lighting system 500, in accordance with embodiments of the present disclosure. As shown in FIG. 5, lighting system 500 may include a voltage supply 504, a dimmer 502, and a lamp assembly 542. Voltage supply 504 may generate a supply voltage V_SUPPLY that is, for example, a nominally 60 Hz/110 V line voltage in the United States of America or a nominally 50 Hz/220 V line voltage in Europe.

Dimmer 502 may comprise any system, device, or apparatus for generating a dimming signal to other elements of lighting system 500, the dimming signal representing a dimming level that causes lighting system 500 to adjust power delivered to a lamp, and, thus, depending on the dimming level, increase or decrease the brightness of lamp 542. Thus, dimmer 502 may include a leading-edge dimmer similar to that depicted in FIG. 1, a trailing-edge dimmer similar to that depicted in FIG. 3, or any other suitable dimmer.

Lamp assembly 542 may comprise any system, device, or apparatus for converting electrical energy (e.g., delivered from dimmer 502) into photonic energy (e.g., at LEDs 532). In some embodiments, lamp assembly 542 may comprise a multifaceted reflector form factor (e.g., an MR16 form factor). In these and other embodiments, lamp assembly 542 may comprise an LED lamp. As shown in FIG. 5, lamp assembly 542 may include a controller 512, a power train 530, and LEDs 532. LEDs 532 may comprise one or more light-emitting diodes configured to emit photonic energy in an amount based on the voltage v_OUT across the LEDs 532.

Power train 530 may comprise any system, device, or apparatus for transferring electrical energy from its input terminals (e.g., from dimmer 502) to a load (e.g., LEDs 532) coupled to its output terminals in conformity with one or more control signals received from controller 512. Thus, in accordance with such one or more control signals, power train 530 may generate an output voltage v_OUT and/or an output current i_OUT for illuminating LEDs 532 or otherwise delivering electrical energy to a suitable load at the output terminals of power train 530. To carry out such functionality, power train 530 may include one or more of a signal rectifier (e.g., a bridge rectifier for rectifying dimmer output signal V_{Φ_DIM}, a boost converter, a buck converter, another type of power converter, a capacitor, and another type of energy storage device.

Controller 512 may comprise any system, device, or apparatus configured to, as described in greater detail elsewhere in this disclosure, determine one or more characteristics (e.g., phase angle of dimmer 502) of voltage V_{Φ_DIM} present at the input of power train 530 and control energy transferred between the input of power train 530 to the output of power train 530 based on characteristics of voltage V_{Φ_DIM}.

In operation, controller 512 may receive and analyze voltage V_{Φ_DIM} to determine a raw, instantaneous phase angle associated with a control setting of dimmer 502, as indicated by phase extraction block 514 shown in FIG. 5. Such raw phase angle values may be filtered as indicated by phase filtering block 516 in order to generate a filtered phase angle. As described in greater detail below, filtering of the extracted phase angle may be performed in conformity with a variable bandwidth filter, as described below in greater detail. Based on the filtered phase angle generated by phase filtering block 516, light output determination/LED control block 518 of controller 512 may generate a control signal for power train 530 such that the light intensity generated by LEDs 532 is in conformity with the filtered phase angle.

FIG. 6 illustrates an example phase filtering combination for use in the lighting system depicted in FIG. 5, in accordance with embodiments of the present disclosure. The elements shown in FIG. 6 may be used alone or in combination with other elements to perform the functionality of phase filtering block 516. In certain embodiments, phase filtering block 516 may be implemented as a discrete-time filter at twice a power line frequency (e.g., 100 Hz or 120 Hz) of voltage power supply V_SUPPLY.

As shown in FIG. 6, a raw phase angle measurement, as extracted by phase extraction block 514, may be filtered by averaging filter 602 or other fixed-bandwidth filter to generate an averaged phase angle. Averaging filter 602 may have a transfer function which rejects high-frequency noise at the power line rate of V_SUPPLY (e.g., dimmer phase variation, noise, etc.). Averaging filter 602 may be followed by a variable bandwidth filter 604, which generates a filtered phase angle from the averaged phase angle in conformity with a variable bandwidth of the variable bandwidth filter, wherein the variable bandwidth is set based on an integrated error between the averaged phase angle and the filtered bandwidth, as described in greater detail below.

As depicted in FIG. 6, variable bandwidth filter 604 may comprise low-pass filters 606a and 606b, an absolute value block 610, a subtractor 612, and a combiner 614. Low-pass filter 606a may generate an output filtered phase angle from the averaged phase angle generated by averaging filter 602 in accordance with a variable bandwidth coefficient C_vlpf which itself is generated based on an error between the averaged phase angle and the filtered phase angle, as described below. The error ERR may be generated by subtractor 612, which may calculate a difference between the averaged phase angle and the filtered phase angle, and then filtered by low-pass filter 606b which may integrate the error ERR in conformity with a bandwidth coefficient C_g, which may be a constant set by a user and/or manufacturer of controller 512. Absolute value block 610 may output an absolute value of the integrated error generated by low-pass filter 606b, wherein such absolute value may be added to a constant coefficient C_vo at combiner 614 or have some other mathematical transform performed on such absolute value in order to generate the variable bandwidth C_vlpf. In some embodiments, the constant C_vo may establish a minimum variable bandwidth for variable bandwidth filter 604. Accordingly, as magnitude of the error ERR increases, so too will the bandwidth of variable bandwidth filter 604. Thus, variable bandwidth filter 604 may be well adapted to allow controller 512 to quickly respond to changes in a control setting of dimmer 502.

In some embodiments, one or both of low-pass filters 606 may be implemented using leaky integrator filters. Possible implementations of leaky integrator filters for use as low-pass filters 606 are shown in FIGS. 7A and 7B.

As used herein, when two or more elements are referred to as “coupled” to one another, such term indicates that such two or more elements are in electronic communication whether connected indirectly or directly, with or without intervening elements.

This disclosure encompasses all changes, substitutions, variations, alterations, and modifications to the example embodiments herein that a person having ordinary skill in the art would comprehend. Similarly, where appropriate, the appended claims encompass all changes, substitutions, variations, alterations, and modifications to the example embodiments herein that a person having ordinary skill in the art would comprehend. Moreover, reference in the appended claims to an apparatus or system or a component of an apparatus or system being adapted to, arranged to, capable of, configured to, enabled to, operable to, or operative to perform a particular function encompasses that apparatus, system, or component, whether or not it or that particular function is activated, turned on, or unlocked, as long as that apparatus, system, or component is so adapted, arranged, capable, configured, enabled, operable, or operative.

All examples and conditional language recited herein are intended for pedagogical objects to aid the reader in understanding the disclosure and the concepts contributed by the inventor to furthering the art, and are construed as being without limitation to such specifically recited examples and conditions. Although embodiments of the present disclosure have been described in detail, it should be understood that various changes, substitutions, and alterations could be made hereto without departing from the spirit and scope of the disclosure.