Multiple-antenna space multiplexing system using enhancement signal detection and method thereof
US20100104047A1
2010-04-29
12/527,644
2008-04-11
✅ Patent granted
US 8,199,863 B2
2012-06-12
WO; PCT/KR2008/002054; 20080411
WO; WO2008/127035; 20081023
Phuong Phu
2029-04-12
Abstract:
The multiple-antenna space multiplexing system using enhancement signal detection comprising: a code modulation module for coding and modulating bit information; a signal transmission module for transmitting the modulated signals; a signal reception module for receiving the signals; a signal form transform module for transforming form of a channel matrix H and the received signal vector r; a signal detection module for detecting the received signals; a signal reconstruction module for reconstructing the detection results of in the signal detection module, and obtaining a detected signal; a demodulation decoding module for demodulating and decoding the output of the signal reconstruction module, and outputting bit information. Compared with the conventional detection methods, the system performance is improved in considering the realization complexity.
Assignee:
- Samsung Electronics Co., Ltd 16,186 🇰🇷 , South Korea
- Beijing Samsung Telecom R&D Center 24 🇨🇳 , China
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Classification:
H04L1/0631 » CPC main
Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity; Space-time coding Receiver arrangements
H04L1/0656 » CPC further
Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity; Space-time coding; Properties of the code Cyclotomic systems, e.g. Bell Labs Layered Space-Time [BLAST]
H04L5/0023 » CPC further
Arrangements affording multiple use of the transmission path; Arrangements for dividing the transmission path; Three-dimensional division Time-frequency-space
H04L25/022 » CPC further
Baseband systems; Details ; arrangements for supplying electrical power along data transmission lines; Channel estimation of frequency response
H04L25/0238 » CPC further
Baseband systems; Details ; arrangements for supplying electrical power along data transmission lines; Channel estimation using blind estimation
H04L25/0242 » CPC further
Baseband systems; Details ; arrangements for supplying electrical power along data transmission lines; Channel estimation channel estimation algorithms using matrix methods
H04L25/03006 » CPC further
Baseband systems; Details ; arrangements for supplying electrical power along data transmission lines; Shaping networks in transmitter or receiver, e.g. adaptive shaping networks Arrangements for removing intersymbol interference
H04L25/03114 » CPC further
Baseband systems; Details ; arrangements for supplying electrical power along data transmission lines; Shaping networks in transmitter or receiver, e.g. adaptive shaping networks; Arrangements for removing intersymbol interference operating in the time domain non-adaptive, i.e. not adjustable, manually adjustable, or adjustable only during the reception of special signals
H04B7/0413 » CPC further
Radio transmission systems, i.e. using radiation field; Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas MIMO systems
H04B7/0669 » CPC further
Radio transmission systems, i.e. using radiation field; Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal using different channel coding between antennas
H04B7/0697 » CPC further
Radio transmission systems, i.e. using radiation field; Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using spatial multiplexing
H04L2025/03426 » CPC further
Baseband systems; Details ; arrangements for supplying electrical power along data transmission lines; Shaping networks in transmitter or receiver, e.g. adaptive shaping networks; Arrangements for removing intersymbol interference characterised by the type of transmission transmission using multiple-input and multiple-output channels
H04L27/06 IPC
Modulated-carrier systems; Amplitude-modulated carrier systems, e.g. using on-off keying; Single sideband or vestigial sideband modulation Demodulator circuits; Receiver circuits
H03D1/06 IPC
Demodulation of amplitude-modulated oscillations; Details Modifications of demodulators to reduce distortion, e.g. by negative feedback
H03K5/01 IPC
Manipulating of pulses not covered by one of the other main groups of this subclass Shaping pulses
H03K6/04 IPC
Manipulating pulses having a finite slope and not covered by one of the other main groups of this subclass Modifying slopes of pulses, e.g. S-correction
H04B1/10 IPC
Details of transmission systems, not covered by a single one of groups - ; Details of transmission systems not characterised by the medium used for transmission; Receivers Means associated with receiver for limiting or suppressing noise or interference
H04L1/00 IPC
Arrangements for detecting or preventing errors in the information received
H04L25/08 IPC
Baseband systems; Details ; arrangements for supplying electrical power along data transmission lines Modifications for reducing interference; Modifications for reducing effects due to line faults ; Receiver end arrangements for detecting or overcoming line faults
H03D1/04 IPC
Demodulation of amplitude-modulated oscillations; Details Modifications of demodulators to reduce interference by undesired signals
Description
BACKGROUND OF THE INVENTION
1. Field of the Invention
This invention relates to transmission of information in a multiple-antenna communication system, especially relates to a technology of transmission and detection for a multiple-antenna signal.
2. Description of the Related Art
With limited spectrum resources, data transmission rate can be improved effectively by using the multiple-antenna space multiplexing BLAST technology.
The existing BLAST detection algorithm may be divided to linear detection (including Zero-Forcing detection (ZF), Minimum Mean Square Error Detection (MMSE) . . . ) and nonlinear detection (including Zero-Forcing and signal Interference Cancellation detection (ZF-SIC), Minimum mean Square Error and signal Interference Cancellation detection (MMSE-SIC) . . . ).
The linear detection method is easy to be realized relatively, while with poor performance. Compared with the linear detection method, the nonlinear detection method may improve the performance of the system. However the significantly increased complexity caused by iterative interference cancellation is the main difficulty for the nonlinear detection to be put into practice.
The following is a simple outline of linear and nonlinear BLAST detection algorithm.
Linear Detection Algorithm
Assuming the received signal is
r=Hs+n,
where, H is a N×M Channel Matrix, s is an M-dimensional transmission signal vector, r is a N-dimensional receipt signal vector, n is a N-dimensional independent white Gaussian noise, M and N are the numbers of system transmitting and receiving antennas.
For Zero-Forcing detection algorithm,
ŝZF=(HHH)−1HHr=s+(HHH)−1HHn.
For MMSE (Minimum mean square error detection) algorithm,
ŝMMSE=(HHH+σ2I)−1HHr=s+(HHH+σ2I)−1HHn.
where, ŝZF and ŝMMSE are M-dimensional vectors of detected signals under different algorithms respectively.
Nonlinear Detection Algorithm
Compared with the linear detection, the nonlinear detection technology may improve the system performance effectively at the price of increase of operation complexity.
The following gives an outline of sequential interference cancellation algorithm in the BLAST nonlinear detection algorithm. The basic principle of this algorithm is to remove the interference coming from the detected parts in the process of detecting the current signals, so as to reduce the impact that interference has on data with smaller signal-to-noise ratio. This principle is similar to the decision feedback equalization.
The following describes the detection process:
For ZF-SIC detector, it will defines that
Gi=H†=(HHH)−1HH,
For MMSE-SIC detector, it will defines that
Gi=H†=(HHH+σI)−1HH.
After Process 1, a decision signal may be obtained:
ki=arg min∥(Gi)j∥2wki=(Gi)kiyki=wkiTriâki=Q(yki) Process 1
In the above process, k1, k2, . . . , kM form a sequence of transmitting antennas in the detection process.
Then, Process 2 is performed and the impact of the detected signals has been removed from the received signals. The new pseudo inverse matrix is determined and the new decision sequence is also determined.
r i + 1 = r i - a ^ k i ( H ) k i ⇒ G i + 1 = H i + 1 † ⇒ k i + 1 = argmin j ∉ { k 1 … k i } ( G i + 1 ) j 2 ⇒ i ← i + 1 Process 2
Then a cyclical process is formed, and the cyclical process includes Process 1 and Process 2, the cyclical process is carrying out on the signals until i=M. Now, all signals have been determined, and the cyclical process is completed.
The BLAST linear detection method is easy to be realized relatively, while with poor performance. Compared with the linear detection method, the nonlinear detection method can improve the performance of the system. However the significantly increased complexity caused by the iterative interference cancellation is the main difficulty for the nonlinear detection to be put into practice.
SUMMARY OF THE INVENTION
This invention provides a BLAST system using enhancement signal detection. Complexity of this system is close to a BLAST system using a traditional linear detector and the performance of system according to present invention is better than the BLAST system using sequential interference cancellation nonlinear detector.
In order to realize the above object, a multiple-antenna space multiplexing system using enhancement signal detection comprising:
a code modulation module for coding and modulating bit information;
a signal transmission module for transmitting the modulated signals;
a signal reception module for receiving the signals;
a signal form transform module for transforming form of channel matrix H and the received signal vector r;
a signal detection module for detecting the received signals;
a signal reconstruction module for reconstructing the detection results of in the signal detection module, and obtaining a detected signal {tilde over (s)};
a demodulation decoding module for demodulating and decoding the output of the signal reconstruction module, and outputting bit information.
Compared with the ZF and the ZF SIC detection method, the BER performance of this system in this invention are improved significantly. Compared with the above detection methods, in this invention, this invention has more advantages in considering the system performance, improvement and realization complexity.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 shows system architecture of transmitting end according to this invention;
FIG. 2 shows system architecture of receiving end and the signaling flow end according to this invention;
FIG. 3 shows bit error rate (BER) performance.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
The system architecture and signaling flow according to this invention are shown in FIG. 1 and FIG. 2.
An outline of this system architecture is described in the followings:
Code modulation module for coding and modulating the bit information.
Signal transmission module for transmitting the modulated signals. The principles of this module consist in that: the signal waiting to be transmitted is s, assuming that quasi-static fading channel H remains the same between adjacent time block T1 and T2. In time block T1, the transmission signal is sT1=Re(s)+jIm(s), in time block T2, the transmission signal is sT2=Im(s)+jRe(s). Re(s) indicates a real part of the complex signal, Im(s) indicates an imaginary part of the complex signal.
Signal reception module for receiving the signals, rT1=HsT1+nT1, rT2=HsT2+nT2.
Signal form transform module for transforming the form of channel matrix H and the received signal vector r:
H 1 = [ Re ( H ) Im ( H ) ] , H 2 = [ - Im ( H ) Re ( H ) ] , r T 1 ′ = [ Re ( r T 1 ) Im ( r T 1 ) ] , r T 2 ′ = [ Re ( r T 2 ) Im ( r T 2 ) ] .
Signal detection module for detecting the received signals:
Re ( s ~ ) = 0.5 × [ H 1 + H 2 + ] [ r T 1 ′ r T 2 ′ ] , Im ( s ~ ) = 0.5 × [ H 1 + H 2 + ] [ r T 1 ′ r T 1 ′ ] . Re ( s ~ )
is a real part of the detected signal, Im(s) is an imaginary part of the detected signal.
Signal reconstruction module for reconstructing the signal detection results, then obtaining the detected signal {tilde over (s)}. The reconstruction principle: {tilde over (s)}=Re({tilde over (s)})+jIm({tilde over (s)}).
Demodulation and decoding module for demodulating and decoding the detected signal, then outputting bit information.
According to the above process, in the process of signal detection of this system, a pseudo inverse detection matrix
[ Re ( H ) - Im ( H ) Im ( H ) Re ( H ) ] +
in conventional detection algorithms is degenerated to
[ Re ( H ) Im ( H ) ] + and [ - Im ( H ) Re ( H ) ] + ,
which will reduce noise raise in the process of detection obviously. At the same time, compared with the conventional linear detection algorithm, the complexity of this system has not been raised obviously. The complexity is far lower than the sequential interference cancellation nonlinear detection algorithm
The following is to prove the rationality of the signaling process in the system according to this invention:
In the following proving process, [ ]+ means matrix pseudo inverse, [ ]H means matrix transpose conjugate.
At the receiving end, assuming rT1=HsT1+nT1, rT2=HsT2+nT2 (1)
Performing equivalent transformation on expression (1)
r T 1 ′ = [ Re ( r T 1 ) Im ( r T 1 ) ] = [ Re ( H ) - Im ( H ) Im ( H ) Re ( H ) ] [ Re ( s T 1 ) Im ( s T 1 ) ] + [ Re ( n T 1 ) Im ( n T 1 ) ] = [ Re ( H ) Im ( H ) ] Re ( s ) + [ - Im ( H ) Re ( H ) ] Im ( s ) + [ Re ( n T 1 ) Im ( n T 1 ) ] ( 2 ) r T 2 ′ = [ Re ( r T 2 ) Im ( r T 2 ) ] = [ Re ( H ) - Im ( H ) Im ( H ) Re ( H ) ] [ Re ( s T 2 ) Im ( s T 2 ) ] + [ Re ( n T 2 ) Im ( n T 2 ) ] = [ Re ( H ) Im ( H ) ] Im ( s ) + [ - Im ( H ) Re ( H ) ] Re ( s ) + [ Re ( n T 2 ) Im ( n T 2 ) ] ( 3 ) Then H 1 + r T 1 ′ = [ Re ( H ) Im ( H ) ] + [ Re ( r T 1 ) Im ( r T 1 ) ] = [ Re ( H ) Im ( H ) ] + ( [ Re ( H ) Im ( H ) ] Re ( s ) + [ - Im ( H ) Re ( H ) ] Im ( s ) + [ Re ( n T 1 ) Im ( n T 1 ) ] ) = Re ( s ) + [ Re ( H ) Im ( H ) ] + [ - Im ( H ) Re ( H ) ] Im ( s ) + [ Re ( H ) Im ( H ) ] + [ Re ( n T 1 ) Im ( n T 1 ) ] ( 4 ) H 2 + r T 1 ′ = [ - Im ( H ) Re ( H ) ] + [ Re ( r T 1 ) Im ( r T 1 ) ] = [ - Im ( H ) Re ( H ) ] + ( [ Re ( H ) Im ( H ) ] Re ( s ) + [ - Im ( H ) Re ( H ) ] Im ( s ) + [ Re ( n T 1 ) Im ( n T 1 ) ] ) = [ - Im ( H ) Re ( H ) ] + [ Re ( H ) Im ( H ) ] Re ( s ) + Im ( s ) + [ - Im ( H ) Re ( H ) ] + [ Re ( n T 1 ) Im ( n T 1 ) ] ( 5 ) H 1 + r T 2 ′ = [ Re ( H ) Im ( H ) ] + [ Re ( r T 2 ) Im ( r T 2 ) ] = [ Re ( H ) Im ( H ) ] + ( [ Re ( H ) Im ( H ) ] Im ( s ) + [ - Im ( H ) Re ( H ) ] Re ( s ) + [ Re ( n T 1 ) Im ( n T 1 ) ] ) = Im ( s ) + [ Re ( H ) Im ( H ) ] + [ - Im ( H ) Re ( H ) ] Re ( s ) + [ Re ( H ) Im ( H ) ] + [ Re ( n T 1 ) Im ( n T 1 ) ] ( 6 ) H 2 + r T 2 ′ = [ - Im ( H ) Re ( H ) ] + [ Re ( r T 1 ) Im ( r T 1 ) ] = [ - Im ( H ) Re ( H ) ] + ( [ Re ( H ) Im ( H ) ] Im ( s ) + [ - Im ( H ) Re ( H ) ] Re ( s ) + [ Re ( n T 1 ) Im ( n T 1 ) ] ) = [ - Im ( H ) Re ( H ) ] + [ Re ( H ) Im ( H ) ] Im ( s ) + Re ( s ) + [ - Im ( H ) Re ( H ) ] + [ Re ( n T 1 ) Im ( n T 1 ) ] ( 7 ) the following is to prove that [ Re ( H ) Im ( H ) ] + [ - Im ( H ) Re ( H ) ] = - [ - Im ( H ) Re ( H ) ] + [ Re ( H ) Im ( H ) ] ( 8 ) [ Re ( H ) Im ( H ) ] + [ - Im ( H ) Re ( H ) ] = ( [ Re H ( H ) Im H ( H ) ] [ Re ( H ) Im ( H ) ] ) - 1 [ Re H ( H ) Im H ( H ) ] [ - Im ( H ) Re ( H ) ] = [ Re H ( H ) Re ( H ) + Im H ( H ) Im ( H ) ] - 1 [ - Re H ( H ) Im ( H ) + Im H ( H ) Re ( H ) ] ( 9 ) [ - Im ( H ) Re ( H ) ] + [ Re ( H ) Im ( H ) ] = ( [ - Im H ( H ) Re H ( H ) ] [ - Im ( H ) Re ( H ) ] ) - 1 [ - Im H ( H ) Re H ( H ) ] [ Re ( H ) Im ( H ) ] = [ Im H ( H ) Im ( H ) + Re H ( H ) Re ( H ) ] - 1 [ - Im H ( H ) Re ( H ) + Re H ( H ) Im ( H ) ] ( 10 )
Expression (8) may be proved from expression (9) and (10).
Then
0.5 × [ H 1 + H 2 + ] [ r T 1 ′ r T 2 ′ ] = 0.5 × [ H 1 + r T 1 ′ + H 2 + r T 2 ′ ] = 0.5 × ( Re ( s ) + [ Re ( H ) Im ( H ) ] + [ - Im ( H ) Re ( H ) ] Im ( s ) + [ Re ( H ) Im ( H ) ] + [ Re ( n T 1 ) Im ( n T 1 ) ] + [ - Im ( H ) Re ( H ) ] + [ Re ( H ) Im ( H ) ] Im ( s ) + Re ( s ) + [ - Im ( H ) Re ( H ) ] + [ Re ( n T 1 ) Im ( n T 1 ) ] ) ( 11 )
From expression (8) and (11), we may get:
Re ( s ~ ) = 0.5 × [ H 1 + H 2 + ] [ r T 1 ′ r T 2 ′ ] ( 12 )
Similarly,
Im ( s ~ ) = 0.5 × [ H 1 + H 2 + ] [ r T 2 ′ r T 1 ′ ] ( 13 )
The detected signal is
{tilde over (s)}=Re({tilde over (s)})+jIm({tilde over (s)}) (14)
This embodiment uses a multiple antenna BLAST communication system consisting of four transmit four receive antennas. The channel is a quasi-static flat Rayleigh fading channel. Assuming channel remains the same between the continuous time block T1 and T2. In the embodiment, the system according to this invention and the BLAST system using ZF detection and ZF SIC detector are all carried out for performance simulation. To ensure a fair performance comparison, on the transmitting end, the system according to this invention uses 16QAM modulation, while ZF and ZF SIC algorithm transmitting end use QPSK modulation.
In the simulation, 1/3 Turbo code is used for coding and decoding in all algorithms.
Claims
What is claimed is:1. A multiple-antenna space multiplexing system using enhancement signal detection comprising:
a code modulation module (101) for coding and modulating bit information;
a signal transmission module (102) for transmitting the modulated signals;
a signal reception module (201) for receiving the signals;
a signal form transform module (202) for transforming form of a channel matrix H and the received signal vector r;
a signal detection module (203) for detecting the received signals;
a signal reconstruction module (204) for reconstructing the detection results of in the signal detection module, and obtaining a detected signal {tilde over (s)};
a demodulation decoding module (205) for demodulating and decoding the output of the signal reconstruction module, and outputting bit information.
2. The system according to claim 1, wherein the signal transmission module transmits signals as following principles:
a signal waiting to be transmitted is s, assuming that quasi-static fading channel H remains the same between adjacent time block T1 and T2;
in time block T1, the transmission signal is sT1=Re(s)+jIm(s);
in time block T2, the transmission signal is sT2=Im(s)+jRe(s), where Re(s) indicates a real part of complex signal, Im(s) indicates an imaginary part of complex signal.
3. The system according to claim 1, wherein a principle of form transforming of the channel matrix H and the received signal vector r is:
H 1 = [ Re ( H ) Im ( H ) ] , H 2 = [ - Im ( H ) Re ( H ) ] , r T 1 ′ = [ Re ( r T 1 ) Im ( r T 1 ) ] , r T 2 ′ = [ Re ( r T 2 ) Im ( r T 2 ) ] .
4. The system according to claim 1, wherein a principle for the signal detection module detecting the received signals is:
Re ( s ~ ) = 0.5 × [ H 1 + H 2 + ] [ r T 1 ′ r T 2 ′ ] , Im ( s ~ ) = 0.5 × [ H 1 + H 2 + ] [ r T 2 ′ r T 1 ′ ] Re ( s ~ )
is a real part of the detected signal, Im({tilde over (s)}) is an imaginary part of the detected signal.
5. The system according to claim 1, wherein a principle for the signal reconstruction module reconstructing the signal detection results is:
Im ( s ~ ) = 0.5 × [ H 1 + H 2 + ] [ r T 2 ′ r T 1 ′ ] .
6. The system according to claim 1, wherein the antenna is an MIMO antenna.
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